IL300
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Linear Optocoupler, High Gain Stability, Wide Bandwidth
DESCRIPTION
The IL300 linear optocoupler consists of an AlGaAs IRLED
irradiating an isolated feedback and an output PIN
photodiode in a bifurcated arrangement. The feedback
photodiode captures a percentage of the LEDs flux and
generates a control signal (IP1) that can be used to servo the
LED drive current. This technique compensates for the
LED’s non-linear, time, and temperature characteristics.
The output PIN photodiode produces an output signal (IP2)
that is linearly related to the servo optical flux created by the
LED.
The time and temperature stability of the input-output
coupler gain (K3) is insured by using matched PIN
photodiodes that accurately track the output flux of the LED.
FEATURES
• Couples AC and DC signals
• 0.01 % servo linearity
• Wide bandwidth, > 200 kHz
• High gain stability, ± 0.005 %/°C typically
• Low input-output capacitance
• Low power consumption, < 15 mW
• Isolation test voltage, 5300 VRMS, 1 s
• Internal insulation distance, > 0.4 mm
• Compliant to RoHS Directive 2002/95/EC and in
accordance to WEEE 2002/96/EC
APPLICATIONS
• Power supply feedback voltage/current
• Medical sensor isolation
• Audio signal interfacing
• Isolated process control transducers
• Digital telephone isolation
AGENCY APPROVALS
• UL file no. E52744, system code H
• DIN EN 60747-5-2 (VDE 0884)
• DIN EN 60747-5-5 (pending) available with option 1
•BSI
•FIMKO
Note
(1) Also available in tubes, do not put “T” on the end.
A
CNC
NC
C
AA
C
1
2
3
4
8
7
6
5
K2
K1
i179026_2
V
DE
i179026
ORDERING INFORMATION
I L300-DEFG-X0##T
PART NUMBER K3 BIN PACKAGE OPTION TAPE
AND
REEL
AGENCY
CERTIFIED/
PACKAGE
K3 BIN
UL, cUL, BSI,
FIMKO 0.557 to 1.618 0.765 to 1.181 0.851 to 1.181 0.765 to 0.955 0.851 to 1.061 0.945 to 1.181 0.851 to 0.955 0.945 to 1.061
DIP-8 IL300 IL300-DEFG - - IL300-EF - IL300-E IL300-F
DIP-8, 400 mil,
option 6 IL300-X006 IL300-DEFG-X006 - - IL300-EF-X006 IL300-FG-X006 IL300-E-X006 IL300-F-X006
SMD-8, option 7 IL300-X007T
(1)
IL300-DEFG-X007T
(1)
IL300-EFG-X007 IL300-DE-X007T IL300-EF-X007T
(1)
- IL300-E-X007T IL300-F-X007
SMD-8, option 9 IL300-X009T
(1)
IL300-DEFG-X009T
(1)
- - IL300-EF-X009T
(1)
- - IL300-F-X009T
(1)
VDE, UL 0.557 to 1.618 0.765 to 1.181 0.851 to 1.181 0.765 to 0.955 0.851 to 1.061 0.945 to 1.181 0.851 to 0.955 0.945 to 1.061
DIP-8 IL300-X001 IL300-DEFG-X001 - - IL300-EF-X001 - IL300-E-X001 IL300-F-X001
DIP-8, 400 mil,
option 6 IL300-X016 IL300-DEFG-X016 - - IL300-EF-X016 - - IL300-F-X016
SMD-8, option 7 IL300-X017 IL300-DEFG-X017T
(1)
- - IL300-EF-X017T
(1)
- IL300-E-X017T IL300-F-X017T
(1)
SMD-8, option 9 - - - - - - - IL300-F-X019T
(1)
> 0.1 mm
10.16 mm
> 0.7 mm
7.62 mm
DIP-8
Option 7
Option 6
Option 9
IL300
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OPERATION DESCRIPTION
A typical application circuit (figure 1) uses an operational
amplifier at the circuit input to drive the LED. The feedback
photodiode sources current to R1 connected to the inverting
input of U1. The photocurrent, IP1, will be of a magnitude to
satisfy the relationship of (IP1 = VIN/R1).
The magnitude of this current is directly proportional to the
feedback transfer gain (K1) times the LED drive current
(VIN/R1 = K1 x IF). The op-amp will supply LED current to
force sufficient photocurrent to keep the node voltage (Vb)
equal to Va.
The output photodiode is connected to a non-inverting
voltage follower amplifier. The photodiode load resistor, R2,
performs the current to voltage conversion. The output
amplifier voltage is the product of the output forward gain
(K2) times the LED current and photodiode load,
R2 (VO = IF x K2 x R2).
Therefore, the overall transfer gain (VO/VIN) becomes the
ratio of the product of the output forward gain (K2) times the
photodiode load resistor (R2) to the product of the feedback
transfer gain (K1) times the input resistor (R1). This reduces
to
VO/VIN = (K2 x R2)/(K1 x R1).
The overall transfer gain is completely independent of the
LED forward current. The IL300 transfer gain (K3) is
expressed as the ratio of the output gain (K2) to the
feedback gain (K1). This shows that the circuit gain
becomes the product of the IL300 transfer gain times the
ratio of the output to input resistors
VO/VIN = K3 (R2/R1).
K1-SERVO GAIN
The ratio of the input photodiode current (IP1) to the LED
current (IF) i.e., K1 = IP1/IF.
K2-FORWARD GAIN
The ratio of the output photodiode current (IP2) to the LED
current (IF), i.e., K2 = IP2/IF.
K3-TRANSFER GAIN
The transfer gain is the ratio of the forward gain to the servo
gain, i.e., K3 = K2/K1.
ΔK3-TRANSFER FAIN LINEARITY
The percent deviation of the transfer gain, as a function of
LED or temperature from a specific transfer gain at a fixed
LED current and temperature.
PHOTODIODE
A silicon diode operating as a current source. The output
current is proportional to the incident optical flux supplied
by the LED emitter. The diode is operated in the photovoltaic
or photoconductive mode. In the photovoltaic mode the
diode functions as a current source in parallel with a forward
biased silicon diode.
The magnitude of the output current and voltage is
dependent upon the load resistor and the incident LED
optical flux. When operated in the photoconductive mode
the diode is connected to a bias supply which reverse
biases the silicon diode. The magnitude of the output
current is directly proportional to the LED incident optical
flux.
LED (LIGHT EMITTING DIODE)
An infrared emitter constructed of AlGaAs that emits at
890 nm operates efficiently with drive current from 500 μA to
40 mA. Best linearity can be obtained at drive currents
between 5 mA to 20 mA. Its output flux typically changes by
- 0.5 %/°C over the above operational current range.
APPLICATION CIRCUIT
Fig. 1 - Typical Application Circuit
iil300_01
8
7
6
5
K1
1
2
3
4
K2
R1 R2
IL300
Vb
Va +
-
U1
Vin
lp1
-
U2
+
lp2
V
out
V
CC
V
CC
V
CC
V
CC
IF
V
c
+
IL300
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Note
• Stresses in excess of the absolute maximum ratings can cause permanent damage to the device. Functional operation of the device is not
implied at these or any other conditions in excess of those given in the operational sections of this document. Exposure to absolute
maximum ratings for extended periods of the time can adversely affect reliability.
ABSOLUTE MAXIMUM RATINGS (Tamb = 25 °C, unless otherwise specified)
PARAMETER TEST CONDITION SYMBOL VALUE UNIT
INPUT
Power dissipation Pdiss 160 mW
Derate linearly from 25 °C 2.13 mW/°C
Forward current IF60 mA
Surge current (pulse width < 10 μs) IPK 250 mA
Reverse voltage VR5V
Thermal resistance Rth 470 K/W
Junction temperature Tj100 °C
OUTPUT
Power dissipation Pdiss 50 mW
Derate linearly from 25 °C 0.65 mW/°C
Reverse voltage VR50 V
Thermal resistance Rth 1500 K/W
Junction temperature Tj100 °C
COUPLER
Total package dissipation at 25 °C Ptot 210 mW
Derate linearly from 25 °C 2.8 mW/°C
Storage temperature Tstg - 55 to + 150 °C
Operating temperature Tamb - 55 to + 100 °C
Isolation test voltage VISO > 5300 VRMS
Isolation resistance VIO = 500 V, Tamb = 25 °C RIO > 1012 Ω
VIO = 500 V, Tamb = 100 °C RIO > 1011 Ω
ELECTRICAL CHARACTERISTICS (Tamb = 25 °C, unless otherwise specified)
PARAMETER TEST CONDITION SYMBOL MIN. TYP. MAX. UNIT
INPUT (LED EMITTER)
Forward voltage IF = 10 mA VF1.25 1.50 V
VF temperature coefficient ΔVF/Δ°C - 2.2 mV/°C
Reverse current VR = 5 V IR1μA
Junction capacitance VF = 0 V, f = 1 MHz Cj15 pF
Dynamic resistance IF = 10 mA ΔVF/ΔIF6Ω
OUTPUT
Dark current Vdet = - 15 V, IF = 0 A ID125nA
Open circuit voltage IF = 10 mA VD500 mV
Short circuit current IF = 10 mA ISC 70 μA
Junction capacitance VF = 0 V, f = 1 MHz Cj12 pF
Noise equivalent power Vdet = 15 V NEP 4 x 10-14 W/√Hz
COUPLER
Input-output capacitance VF = 0 V, f = 1 MHz 1 pF
K1, servo gain (IP1/IF)I
F = 10 mA, Vdet = - 15 V K1 0.0050 0.007 0.011
Servo current (1)(2) IF = 10 mA, Vdet = - 15 V IP1 70 μA
K2, forward gain (IP2/IF)I
F = 10 mA, Vdet = - 15 V K2 0.0036 0.007 0.011
Forward current IF = 10 mA, Vdet = - 15 V IP2 70 μA
K3, transfer gain (K2/K1) (1)(2) IF = 10 mA, Vdet = - 15 V K3 0.56 1 1.65 K2/K1
IL300
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Notes
• Minimum and maximum values were tested requierements. Typical values are characteristics of the device and are the result of engineering
evaluation. Typical values are for information only and are not part of the testing requirements.
(1) Bin sorting:
K3 (transfer gain) is sorted into bins that are ± 6 % , as follows:
Bin A = 0.557 to 0.626
Bin B = 0.620 to 0.696
Bin C = 0.690 to 0.773
Bin D = 0.765 to 0.859
Bin E = 0.851 to 0.955
Bin F = 0.945 to 1.061
Bin G = 1.051 to 1.181
Bin H = 1.169 to 1.311
Bin I = 1.297 to 1.456
Bin J = 1.442 to 1.618
K3 = K2/K1. K3 is tested at IF = 10 mA, Vdet = - 15 V.
(2) Bin categories: All IL300s are sorted into a K3 bin, indicated by an alpha character that is marked on the part. The bins range from “A”
through “J”.
The IL300 is shipped in tubes of 50 each. Each tube contains only one category of K3. The category of the parts in the tube is marked on
the tube label as well as on each individual part.
(3) Category options: standard IL300 orders will be shipped from the categories that are available at the time of the order. Any of the ten
categories may be shipped. For customers requiring a narrower selection of bins, the bins can be grouped together as follows:
IL300-DEFG: order this part number to receive categories D, E, F, G only.
IL300-EF: order this part number to receive categories E, F only.
IL300-E: order this part number to receive category E only.
COUPLER
Transfer gain stability IF = 10 mA, Vdet = - 15 V ΔK3/ΔTA± 0.005 ± 0.05 %/°C
Transfer gain linearity
IF = 1 mA to 10 mA ΔK3 ± 0.25 %
IF = 1 mA to 10 mA,
Tamb = 0 °C to 75 °C ± 0.5 %
PHOTOCONDUCTIVE OPERATION
Frequency response IFq = 10 mA, MOD = ± 4 mA,
RL = 50 ΩBW (- 3 db) 200 kHz
Phase response at 200 kHz Vdet = - 15 V - 45 Deg.
SWITCHING CHARACTERISTICS
PARAMETER TEST CONDITION SYMBOL MIN. TYP. MAX. UNIT
Switching time ΔIF = 2 mA, IFq = 10 mA tr1μs
tf1μs
Rise time tr1.75 μs
Fall time tf1.75 μs
ELECTRICAL CHARACTERISTICS (Tamb = 25 °C, unless otherwise specified)
PARAMETER TEST CONDITION SYMBOL MIN. TYP. MAX. UNIT
COMMON MODE TRANSIENT IMMUNITY
PARAMETER TEST CONDITION SYMBOL MIN. TYP. MAX. UNIT
Common mode capacitance VF = 0 V, f = 1 MHz CCM 0.5 pF
Common mode rejection ratio f = 60 Hz, RL = 2.2 kΩCMRR 130 dB
IL300
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TYPICAL CHARACTERISTICS (Tamb = 25 °C, unless otherwise specified)
Fig. 2 - LED Forward Current vs. Forward Voltage
Fig. 3 - Servo Photocurrent vs. LED Current and Temperature
Fig. 4 - Normalized Servo Photocurrent vs.
LED Current and Temperature
Fig. 5 - Servo Gain vs. LED Current and Temperature
Fig. 6 - Normalized Transfer Gain vs.
LED Current and Temperature
Fig. 7 - Amplitude Response vs. Frequency
iil300_02
1.41.31.21.1
0
5
10
15
20
25
30
35
VF - LED Forward Voltage (V)
IF - LED Current (mA)
1.0
iil300_04
0 °C
25 °C
50 °C
75 °C
0.1 1 10 100
300
250
200
150
100
50
0
IF - LED Current (mA)
IP1 - Servo Photocurrent (µA)
VD = - 15 V
iil300_06
010152025
3.0
2.5
2.0
1.5
1.0
0.5
0.0
I
F
- LED Current (mA)
Normalized Photocurrent
Normalized to: IP1 at IF = 10 mA
TA = 25 °C
VD = - 15 V
0 °C
25 °C
50 °C
75 °C
5
IF- L ED Current (mA)
0.1 1 10 100
0
K1- Ser vo Gain - I
P1
/I
F
0.010
0.008
0.006
0.004
0.002
0°
25°
50°
75°
100°
17754
iil300_11
010152025
1.010
1.005
1.000
0.995
0.990
IF - LED Current (mA)
K3 - Transfer Gain - (K2/K1)
0 °C
25 °C
50 °C
75 °C
Normalized to:
IF = 10 mA
TA = 25 °C
5
iil300_12
104105106
5
0
- 5
- 10
- 15
- 20
F - Frequency (Hz)
Amplitude Response (dB)
RL = 1 kΩ
IF = 10 mA, Mod = ± 2.0 Ma (peak)
RL = 10 kΩ
IL300
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Fig. 8 - Amplitude and Phase Response vs. Frequency
Fig. 9 - Common-Mode Rejection
Fig. 10 - Photodiode Junction Capacitance vs.
Reverse Voltage
APPLICATION CONSIDERATIONS
In applications such as monitoring the output voltage from a
line powered switch mode power supply, measuring
bioelectric signals, interfacing to industrial transducers, or
making floating current measurements, a galvanically
isolated, DC coupled interface is often essential. The IL300
can be used to construct an amplifier that will meet these
needs.
The IL300 eliminates the problems of gain nonlinearity and
drift induced by time and temperature, by monitoring LED
output flux.
A pin photodiode on the input side is optically coupled to the
LED and produces a current directly proportional to flux
falling on it. This photocurrent, when coupled to an amplifier,
provides the servo signal that controls the LED drive current.
The LED flux is also coupled to an output PIN photodiode.
The output photodiode current can be directly or amplified
to satisfy the needs of succeeding circuits.
ISOLATED FEEDBACK AMPLIFIER
The IL300 was designed to be the central element of DC
coupled isolation amplifiers. Designing the IL300 into an
amplifier that provides a feedback control signal for a line
powered switch mode power is quite simple, as the
following example will illustrate.
See figure 12 for the basic structure of the switch mode
supply using the Infineon TDA4918 push-pull switched
power supply control cChip. Line isolation are provided by
the high frequency transformer. The voltage monitor
isolation will be provided by the IL300.
The isolated amplifier provides the PWM control signal
which is derived from the output supply voltage. Figure 13
more closely shows the basic function of the amplifier.
The control amplifier consists of a voltage divider and a
non-inverting unity gain stage. The TDA4918 data sheet
indicates that an input to the control amplifier is a high
quality operational amplifier that typically requires a + 3 V
signal. Given this information, the amplifier circuit topology
shown in figure 14 is selected.
The power supply voltage is scaled by R1 and R2 so that
there is + 3 V at the non-inverting input (Va) of U1. This
voltage is offset by the voltage developed by photocurrent
flowing through R3. This photocurrent is developed by the
optical flux created by current flowing through the LED.
Thus as the scaled monitor voltage (Va) varies it will cause a
change in the LED current necessary to satisfy the
differential voltage needed across R3 at the inverting input.
The first step in the design procedure is to select the value
of R3 given the LED quiescent current (IFq) and the servo
gain (K1). For this design, IFq = 12 mA. Figure 4 shows the
servo photocurrent at IFq is found to be 100 mA. With this
data R3 can be calculated.
iil300_13
dB
Phase
Ø - Phase Response (°)
103104105106107
5
0
- 5
- 10
- 15
- 20
45
0
- 45
- 90
- 135
- 180
F - Frequency (Hz)
Amplitude Response (dB)
IFq = 10 mA
Mod = ± 4.0 mA
TA = 25 °C
RL = 50 Ω
iil300_15
0
2
4
6
8
10
12
14
Voltage (Vdet)
Capacitance (pF)
048
2610
R3 Vb
IPI
------ 3 V
100 μA
------------------ 30 kΩ== =
IL300
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Fig. 11 - Isolated Control Amplifier
For best input offset compensation at U1, R2 will equal R3.
The value of R1 can easily be calculated from the following.
The value of R5 depends upon the IL300 Transfer Gain (K3).
K3 is targeted to be a unit gain device, however to minimize
the part to part Transfer Gain variation, Infineon offers K3
graded into ± 5 % bins. R5 can determined using the
following equation,
or if a unity gain amplifier is being designed
(VMONITOR = VOUT, R1 = 0), the equation simplifies to:
Fig. 12 - Switching Mode Power Supply
Fig. 13 - DC Coupled Power Supply Feedback Amplifier
iil300_16
+
-
Voltage
monitor
R1
R2
To control
input
ISO
AMP
+1
R1 R2 x VMONITOR
Va
------------------------- - 1


=
R5 VOUT
VMONITOR
--------------------------- x R3 x R1 R2+()
R2 x K3
-----------------------------------------
=
R5 R3
K3
-------
=
iil300_17
Switch Xformer
Switch
mode
regulator
TDA4918
Isolated
feedback
Control
110/
220
main
DC output
AC/DC
rectifier
AC/DC
rectifier
iil300_18
8
7
6
5
100 pF
4
3
1
2
8
6
7
K1
VCC
VCC
1
2
3
4
K2
VCC
Vmonitor
R1
20 kΩ
R2
30 kΩ
R3
30 kΩ
R4
100 Ω
Vout To
control
input
R5
30 kΩ
IL300
Vb
Va
+
-
U1
LM201
IL300
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Table 1. Gives the value of R5 given the production K3 bin.
The last step in the design is selecting the LED current
limiting resistor (R4). The output of the operational amplifier
is targeted to be 50 % of the VCC, or 2.5 V. With an LED
quiescent current of 12 mA the typical LED (VF) is 1.3 V.
Given this and the operational output voltage, R4 can be
calculated.
The circuit was constructed with an LM201 differential
operational amplifier using the resistors selected. The
amplifier was compensated with a 100 pF capacitor
connected between pins 1 and 8.
The DC transfer characteristics are shown in figure 17. The
amplifier was designed to have a gain of 0.6 and was
measured to be 0.6036. Greater accuracy can be achieved
by adding a balancing circuit, and potentiometer in the input
divider, or at R5. The circuit shows exceptionally good gain
linearity with an RMS error of only 0.0133 % over the input
voltage range of 4 V to 6 V in a servo mode; see figure 15.
Fig. 14 - Transfer Gain
Fig. 15 - Linearity Error vs. Input Voltage
The AC characteristics are also quite impressive offering a
- 3 dB bandwidth of 100 kHz, with a - 45° phase shift at
80 kHz as shown in figure 16.
TABLE 1 - R5 SELECTION
BIN K3 R5 RESISTOR
MIN. MAX. TYP. 1 % kΩ
A 0.560 0.623 0.59 51.1
B 0.623 0.693 0.66 45.3
C 0.693 0.769 0.73 41.2
D 0.769 0.855 0.81 37.4
E 0.855 0.950 0.93 32.4
F 0.950 1.056 1 30
G 1.056 1.175 1.11 27
H 1.175 1.304 1.24 24
I 1.304 1.449 1.37 22
J 1.449 1.610 1.53 19.4
R4 Vopamp - VF
IFq
---------------------------------2.5 V - 1.3 V
12 mA
--------------------------------- 100 Ω===
iil300_19
6.05.55.04.54.0
2.25
2.50
2.75
3.00
3.25
3.50
3.75
Vout - Output Voltage (V)
Vout = 14.4 mV + 0.6036 x Vin
LM 201 Ta = 25 °C
iil300_20
6.05.55.04.54.0
- 0.015
- 0.010
- 0.005
0.000
0.005
0.010
0.015
0.020
0.025
Vin - Input Voltage (V)
Linearity Error (%)
LM201
IL300
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Fig. 16 - Amplitude and Phase Power Supply Control
The same procedure can be used to design isolation
amplifiers that accept bipolar signals referenced to ground.
These amplifiers circuit configurations are shown in
figure 17. In order for the amplifier to respond to a signal that
swings above and below ground, the LED must be pre
biased from a separate source by using a voltage reference
source (Vref1). In these designs, R3 can be determined by the
following equation.
Fig. 17 - Non-inverting and Inverting Amplifiers
iil300_21
dB
Phase
Phase Response (°)
103104105106
2
0
- 2
- 4
- 6
- 8
45
0
- 45
- 90
- 135
- 180
F - Frequency (Hz)
Amplitude Response (dB)
R3 Vref1
IP1
----------- Vref1
K1IFq
---------------
==
TABLE 2 - OPTOLINEAR AMPLIEFIERS
AMPLIFIER INPUT OUTPUT GAIN OFFSET
Non-inverting
Inverting Inverting
Non-inverting Non-inverting
Inverting
Inverting Non-inverting
Non-inverting Inverting
iil300_22
Vcc
20 pF
4
1
2
3
4
8
7
6
5
+ Vref2
R5
R6
7
2
4
3Vo
R4
R3
- Vref1
Vin
R1 R2
37
6
+
+Vcc
100 Ω
6
IL 300
2- V
cc
- V
cc
Vcc
- Vcc
+
Vcc
20 pF
4
1
2
3
4
8
7
6
5
+ Vref2
7
2
4
3
Vout
R4
R3
+ Vref1
Vin
R1 R2
37
6
+
+ Vcc
100 Ω
6
2Vcc Vcc
- V
cc
+
Vcc
–
–
Non-inverting input Non-inverting output
Inverting input Inverting output
IL 300
–
–
- Vcc
Vcc
VOUT
VIN
------------- K3 x R4 x R2
R3 x R1 x R2()
------------------------------------------
=
Vref2
Vref1 x R4 x K3
R3
------------------------------------------
=
VOUT
VIN
------------- K3 x R4 x R2 x R5 + R6()
R3 x R5 x R1 x R2()
-------------------------------------------------------------------------
=
Vref2
- Vref1 x R4 x R5 + R6() x K3
R3 x R6
----------------------------------------------------------------------------------
=
VOUT
VIN
------------- - K3 x R4 x R2 x R5 + R6()
R3 x R1 x R2()
------------------------------------------------------------------------------
=
Vref2
Vref1 x R4 x R5 + R6() x K3
R3 x R6
------------------------------------------------------------------------------
=
VOUT
VIN
------------- - K3 x R4 x R2
R3 x R1 x R2()
------------------------------------------
=
Vref2
- Vref1 x R4 x K3
R3
----------------------------------------------
=
IL300
www.vishay.com Vishay Semiconductors
Rev. 1.7, 23-Sep-11 10 Document Number: 83622
For technical questions, contact: optocoupleranswers@vishay.com
THIS DOCUMENT IS SUBJECT TO CHANGE WITHOUT NOTICE. THE PRODUCTS DESCRIBED HEREIN AND THIS DOCUMENT
ARE SUBJECT TO SPECIFIC DISCLAIMERS, SET FORTH AT www.vishay.com/doc?91000
These amplifiers provide either an inverting or non-inverting
transfer gain based upon the type of input and output
amplifier. Table 2 shows the various configurations along
with the specific transfer gain equations. The offset column
refers to the calculation of the output offset or Vref2
necessary to provide a zero voltage output for a zero voltage
input. The non-inverting input amplifier requires the use of a
bipolar supply, while the inverting input stage can be
implemented with single supply operational amplifiers that
permit operation close to ground.
For best results, place a buffer transistor between the LED
and output of the operational amplifier when a CMOS
opamp is used or the LED IFq drive is targeted to operate
beyond 15 mA. Finally the bandwidth is influenced by the
magnitude of the closed loop gain of the input and output
amplifiers. Best bandwidths result when the amplifier gain is
designed for unity.
PACKAGE DIMENSIONS in millimeters
PACKAGE MARKING (this is an example of the IL300-E-X001)
i178010
ISO method A
Pin one ID
3
4
10°
1
2
4°
3°
9
6
5
8
7
0.527
0.889
3.302
3.810
0.406
0.508
7.112
8.382
1.016
1.270
9.652
10.16
0.203
0.305
2.794
3.302
6.096
6.604
0.508 ref. 0.254 ref.
0.254 ref.
2.540
1.270
7.62 typ.
8 min.
0.51
1.02
7.62 ref.
9.53
10.03
0.25 typ.
0.102
0.249
15° max.
Option 9
0.35
0.25
10.16
10.92
7.8
7.4
10.36
9.96
Option 6
8 min.
7.62 typ.
4.6
4.1
8.4 min.
10.3 max.
0.7
Option 7
18450
IL300-E
V YWW H 68
X001
Legal Disclaimer Notice
www.vishay.com Vishay
Revision: 02-Oct-12 1Document Number: 91000
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